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rev. information furnished by analog devices is believed to be accurate and reliable. however, no responsibility is assumed by analog devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. no license is granted by implication or otherwise under any patent or patent rights of analog devices. a ad8350 one technology way, p.o. box 9106, norwood, ma 02062-9106, u.s.a. tel: 781/329-4700 www.analog.com fax: ? analog devices, inc., low distortion 1.0 ghz differential amplifier features high dynamic range output ip3: +28 dbm: re 50 @ 250 mhz low noise figure: 5.9 db @ 250 mhz two gain versions: ad8350-15: 15 db ad8350-20: 20 db C3 db bandwidth: 1.0 ghz single supply operation: 5 v to 10 v supply current: 28 ma input/output impedance: 200 single-ended or differential input drive 8-lead soic package and 8-lead microsoic package applications cellular base stations communications receivers rf/if gain block differential a-to-d driver saw filter interface single-ended-to-differential conversion high performance video high speed data transmission product description the ad8350 series are high performance fully-differential amplifiers useful in rf and if circuits up to 1000 mhz. the amplifier has excellent noise figure of 5.9 db at 250 mhz. it offers a high output third order intercept (oip3) of +28 dbm at 250 mhz. gain versions of 15 db and 20 db are offered. the ad8350 is designed to meet the demanding performance requirements of communications transceiver ap plications. it enables a high dynamic range differential signal chain, with exceptional linearity and increased common-mode rejection. the device can be used as a general purpose gain block, an a-to-d driver, and high speed data interface driver, among other functions. the ad8350 input can also be used as a single- ended-to-differential converter. the amplifier can be operated down to 5 v with an oip3 of +28 dbm at 250 mhz and slightly reduced distor tion perfor- mance. the wide bandwidth, high dynamic range and tempe rature stability make this product ideal for the various rf and if frequencies required in cellular, catv, broadband, instrumen- tation and other applications. the ad8350 is offered in an 8-lead single soic package and soic package. it operates from 5 v and 10 v power supplies, drawing 28 ma typical. the ad8350 offers a power enable func- tion for pow er-sensitive applications. the ad8350 is fabricated using analog devices?proprietary high speed complementary bipolar process. the device is available in the industrial (40 c to +85 c) temperature range. functional block diagram 8-lead soic and soic packages (with enable) 1 2 3 4 8 7 6 5 ad8350 in+ in enbl out+ out v cc gnd + gnd 2013 781/461-3113 b
rev. C2C ad8350?pecifications (@ 25 c, v s = 5 v, g = 15 db, unless otherwise noted. all specifications refer to differential inputs and differential outputs unless noted.) parameter conditions min typ max unit dynamic performance ? db bandwidth v s = 5 v, v out = 1 v p-p 0.9 ghz v s = 10 v, v out = 1 v p-p 1.1 ghz bandwidth for 0.1 db flatness v s = 5 v, v out = 1 v p-p 90 mhz v s = 10 v, v out = 1 v p-p 90 mhz slew rate v out = 1 v p-p 2000 v/ s settling time 0.1%, v out = 1 v p-p 10 ns gain (s21) 1 v s = 5 v, f = 50 mhz 14 15 16 db gain supply sensitivity v s = 5 v to 10 v, f = 50 mhz 0.003 db/v gain temperature sensitivity t min to t max ?.002 db/ c isolation (s12) 1 f = 50 mhz ?8 db noise/harmonic performance 50 mhz signal second harmonic v s = 5 v, v out = 1 v p-p ?6 dbc v s = 10 v, v out = 1 v p-p ?7 dbc third harmonic v s = 5 v, v out = 1 v p-p ?5 dbc v s = 10 v, v out = 1 v p-p ?0 dbc output second order intercept 2 v s = 5 v 58 dbm v s = 10 v 58 dbm output third order intercept 2 v s = 5 v 28 dbm v s = 10 v 29 dbm 250 mhz signal second harmonic v s = 5 v, v out = 1 v p-p ?8 dbc v s = 10 v, v out = 1 v p-p ?9 dbc third harmonic v s = 5 v, v out = 1 v p-p ?2 dbc v s = 10 v, v out = 1 v p-p ?1 dbc output second order intercept 2 v s = 5 v 39 dbm v s = 10 v 40 dbm output third order intercept 2 v s = 5 v 24 dbm v s = 10 v 28 dbm 1 db compression point (rti) 2 v s = 5 v 2 dbm v s = 10 v 5 dbm voltage noise (rti) f = 150 mhz 1.7 nv/ hz noise figure f = 150 mhz 6.8 db input/output characteristics differential offset voltage (rti) v out+ ?v out 1mv differential offset drift t min to t max 0.02 mv/ c input bias current 15 a input resistance real 200 ? cmrr f = 50 mhz ?7 db output resistance real 200 ? power supply operating range 41 1 . 0 v quiescent current powered up, v s = 5 v 25 28 32 ma powered down, v s = 5 v 3 3.8 5.5 ma powered up, v s = 10 v 27 30 34 ma powered down, v s = 10 v 3 4 6.5 ma power-up/down switching 15 ns power supply rejection ratio f = 50 mhz, v s ? = 1 v p-p ?8 db operating temperature range ?0 +85 c notes 1 see tables ii?ii for complete list of s-parameters. 2 re: 50 ? . specifications subject to change without notice. b
rev. C3C ad8350 (@ 25 c, v s = 5 v, g = 20 db, unless otherwise noted. all specifications refer to differential inputs and differential outputs unless noted.) ad8350-20?pecifications parameter conditions min typ max unit dynamic performance ? db bandwidth v s = 5 v, v out = 1 v p-p 0.7 ghz v s = 10 v, v out = 1 v p-p 0.9 ghz bandwidth for 0.1 db flatness v s = 5 v, v out = 1 v p-p 90 mhz v s = 10 v, v out = 1 v p-p 90 mhz slew rate v out = 1 v p-p 2000 v/ s settling time 0.1%, v out = 1 v p-p 15 ns gain (s21) 1 v s = 5 v, f = 50 mhz 19 20 21 db gain supply sensitivity v s = 5 v to 10 v, f = 50 mhz 0.003 db/v gain temperature sensitivity t min to t max ?.002 db/ c isolation (s12) 1 f = 50 mhz ?2 db noise/harmonic performance 50 mhz signal second harmonic v s = 5 v, v out = 1 v p-p ?5 dbc v s = 10 v, v out = 1 v p-p ?6 dbc third harmonic v s = 5 v, v out = 1 v p-p ?6 dbc v s = 10 v, v out = 1 v p-p ?0 dbc output second order intercept 2 v s = 5 v 56 dbm v s = 10 v 56 dbm output third order intercept 2 v s = 5 v 28 dbm v s = 10 v 29 dbm 250 mhz signal second harmonic v s = 5 v, v out = 1 v p-p ?5 dbc v s = 10 v, v out = 1 v p-p ?6 dbc third harmonic v s = 5 v, v out = 1 v p-p ?5 dbc v s = 10 v, v out = 1 v p-p ?0 dbc output second order intercept 2 v s = 5 v 37 dbm v s = 10 v 38 dbm output third order intercept 2 v s = 5 v 24 dbm v s = 10 v 28 dbm 1 db compression point (rti) 2 v s = 5 v ?.6 dbm v s = 10 v 1.8 dbm voltage noise (rti) f = 150 mhz 1.7 nv/ hz noise figure f = 150 mhz 5.6 db input/output characteristics differential offset voltage (rti) v out+ ?v out 1mv differential offset drift t min to t max 0.02 mv/ c input bias current 15 a input resistance real 200 ? cmrr f = 50 mhz ?2 db output resistance real 200 ? power supply operating range 41 1 . 0 v quiescent current powered up, v s = 5 v 25 28 32 ma powered down, v s = 5 v 3 3.8 5.5 ma powered up, v s = 10 v 27 30 34 ma powered down, v s = 10 v 3 4 6.5 ma power-up/down switching 15 ns power supply rejection ratio f = 50 mhz, v s ? = 1 v p-p ?5 db operating temperature range ?0 +85 c notes 1 see tables ii?ii for complete list of s-parameters. 2 re: 50 ? . b
rev. ad8350 C4C caution esd (electrostatic discharge) sensitive device. electrostatic charges as high as 4000 v readily accumulate on the human body and test equipment and can discharge without detection. although the ad8350 features proprietary esd protection circuitry, permanent damage may occur on devices subjected to high-energy electrostatic discharges. therefore, proper esd precautions are recommended to avoid performance degradation or loss of functionality. warning! esd sensitive device pin function descriptions pin function description 1, 8 in+, in differential inputs. in+ and in should be ac-coupled (pins have a dc bias of midsupply). differential input impedance is 200 ? . 2 enbl po wer-up pin. a high level (5 v) en ables the device; a low level (0 v) puts device in sleep mode. 3v cc positive supply voltage. 5 v to 10 v. 4, 5 out+, out differential outputs. out+ and out?should be ac-coupled (pins have a dc bias of midsupply). differential input impedance is 200 ? . 6, 7 gnd common external ground reference. absolute maximum ratings * supply voltage, v s . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 11 v input power differential . . . . . . . . . . . . . . . . . . . . . . +8 dbm internal power dissipation . . . . . . . . . . . . . . . . . . . . 400 mw ja soic (r) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 100 c/w ja soic (rm) . . . . . . . . . . . . . . . . . . . . . . . . . . . . 133 c/w maximum junction temperature . . . . . . . . . . . . . . . . . 125 c operating temperature range . . . . . . . . . . . ?0 c to +85 c storage temperature range . . . . . . . . . . . . ?5 c to +150 c lead temperature range (soldering 60 sec) . . . . . . . . . 300 c * stresses above those listed under absolute maximum ratings may cause perma- nent damage to the device. this is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. exposure to absolute maximum rating conditions for extended periods may affect device reliability. pin configuration top view (not to scale) 8 7 6 5 1 2 3 4 in+ enbl v cc out+ in gnd gnd out ad8350 b
rev. C5C typical performance characteristics ad8350 temperature c supply current ma 50 40 40 30 20 10 0 20 0 20 40 60 80 v cc = 5v v cc = 10v tpc 1. supply current vs. temperature frequency mhz impedance 350 1 300 250 200 150 100 10 100 1k v cc = 10v v cc = 5v tpc 4. ad8350-15 input imped- ance vs. frequency frequency mhz impedance 800 0 0 10 1000 100 200 400 600 soic soic tpc 7. ad8350-20 output imped- ance vs. frequency frequency mhz gain db 20 1 15 10 5 0 10 100 1k 10k v cc = 10v v cc = 5v tpc 2. ad8350-15 gain (s21) vs. frequency frequency mhz impedance 350 1 300 250 200 150 100 10 100 1k v cc = 10v v cc = 5v tpc 5. ad8350-20 input impedance vs. frequency frequency mhz isolation db 5 1 10 15 20 25 10 100 1k 10k v cc = 10v v cc = 5v tpc 8. ad8350-15 isolation (s12) vs. frequency frequency mhz gain db 25 1 20 15 10 5 10 100 1k 10k v cc = 10v v cc = 5v tpc 3. ad8350-20 gain (s21) vs. frequency frequency mhz impedance 500 100 0 0 10 1000 100 200 300 400 soic soic tpc 6. ad8350-15 output impedance vs. frequency frequency mhz isolation db 10 1 15 20 25 30 10 100 1k 10k v cc = 10v v cc = 5v tpc 9. ad8350-20 isolation (s12) vs. frequency b
rev. ad8350 C6C fundamental frequency mhz distortion dbc 40 0 45 50 55 60 65 70 75 80 50 100 150 200 250 300 v out = 1v p-p hd3 (v cc = 10v) hd3 (v cc = 5v) hd2 (v cc = 5v) hd2 (v cc = 10v) tpc 10. ad8350-15 harmonic distortion vs. frequency output voltage v p - p distortion dbc 45 0 55 65 75 85 0.5 1 1.5 2 2.5 3 3.5 f o = 50mhz hd3 (v cc = 10v) hd3 (v cc = 5v) hd2 (v cc = 5v) hd2 (v cc = 10v) tpc 13. ad8350-20 harmonic distor- tion vs. differential output voltage frequency mhz oip3 dbm (re: 50) 41 0 50 100 150 200 250 300 36 31 26 21 16 11 v cc = 10v v cc = 5v tpc 16. ad8350-15 output referred ip3 vs. frequency fundamental frequency mhz distortion dbc 40 0 45 50 55 60 65 70 75 80 50 100 150 200 250 300 v out = 1v p-p hd3 (v cc = 10v) hd3 (v cc = 5v) hd2 (v cc = 5v) hd2 (v cc = 10v) tpc 11. ad8350-20 harmonic dis- tortion vs. frequency frequency mhz oip2 dbm (re: 50) 66 0 50 100 150 200 250 300 61 56 51 46 41 36 v cc = 10v v cc = 5v tpc 14. ad8350-15 output referred ip2 vs. frequency frequency mhz oip3 dbm (re: 50) 41 0 50 100 150 200 250 300 36 31 26 21 16 11 v cc = 10v v cc = 5v tpc 17. ad8350-20 output referred ip3 vs. frequency output voltage v p-p distortion dbc 45 0 55 65 75 85 0.5 1 1.5 2 2.5 3 3.5 f o = 50mhz hd3 (v cc = 10v) hd3 (v cc = 5v) hd2 (v cc = 5v) hd2 (v cc = 10v) tpc 12. ad8350-15 harmonic distor- tion vs. differential output voltage frequency mhz oip2 dbm (re: 50) 66 0 50 100 150 200 250 300 61 56 51 46 41 36 v cc = 10v v cc = 5v tpc 15. ad8350-20 output referred ip2 vs. frequency frequency mhz 1db compression dbm (re: 50) 0 100 200 300 400 500 600 7.5 5.0 2.5 0 2.5 5.0 v cc = 10v v cc = 5v input referred 10.0 tpc 18. ad8350-15 1 db compres- sion vs. frequency b
rev. ad8350 C7C frequency mhz 1db compression dbm (re: 50 ) 0 100 200 300 400 500 600 7.5 5.0 2.5 0 2.5 5.0 v cc = 10v v cc = 5v input referred 7.5 tpc 19. ad8350-20 1 db compres- sion vs. frequency v cc volts 1 gain db 25 20 15 10 5 0 5 10 15 20 2345678910 ad8350-20 ad8350-15 tpc 22. ad8350 gain (s21) vs. supply voltage frequency mhz psrr db 20 1 30 40 50 60 70 80 90 10 100 1k v cc = 5v ad8350-20 ad8350-15 tpc 25. ad8350 cmrr vs. frequency frequency mhz noise figure db 10 0 50 100 150 200 250 300 350 400 450 500 9 8 7 6 5 v cc = 10v v cc = 5v tpc 20. ad8350-15 noise figure vs. frequency temperature c output offset mv 100 40 50 0 50 100 150 200 250 20 0 20 40 60 80 v out (v cc = 5v) v out (v cc = 10v) v out + (v cc = 10v) v out + (v cc = 5v) tpc 23. ad8350 output offset volt- age vs. temperature 5v v cc = 5v 500mv 30ns v out enbl tpc 26. ad8350 power-up/down response time frequency mhz noise figure db 10 0 50 100 150 200 250 300 350 400 450 500 9 8 7 6 5 v cc = 10v v cc = 5v tpc 21. ad8350-20 noise figure vs. frequency frequency mhz psrr db 20 1 30 40 50 60 70 80 90 10 100 1k v cc = 5v ad8350-20 ad8350-15 tpc 24. ad8350 psrr vs. frequency b
rev. ad8350 C8C applications using the ad8350 figure 1 shows the basic connections for operating the ad 8350. a single supply in the range 5 v to 10 v is required. the power supply pin should be decoupled using a 0.1 f capacitor. the enbl pin is tied to the positive supply or to 5 v (when v cc = 10 v) for normal operation and should be pulled to gr ound to put the device in sleep mode. both the inputs and the o utputs have dc bias levels at midsupply and should be ac-coupled. also shown in figure 1 are the impedance balancing requireme nts, either resistive or reactive, of the input and output. with an input and output impedance of 200 ? , the ad8350 should be driven by a 200 ? source and loaded by a 200 ? impedance. a reactive match can also be implemented. 8 7 6 5 1 2 3 4 ad8350 + enbl (5v) +v s (5v to 10v) c5 0.1f c4 0.001f c3 0.001f load z = 200 c2 0.001f c1 0.001f source z = 100 z = 100 figure 1. basic connections for differential drive figure 2 shows how the ad8350 can be driven by a single- ended source. the unused input should be ac-coupled to ground. when driven single-endedly, there will be a slight imbalance in the differential output voltages. this will cause an increase in the second order harmonic distortion (at 50 mhz, with v cc = 10 v and v out = 1 v p-p, ?9 dbc was measured for the second harmonic on ad8350-15). 8 7 6 5 1 2 3 4 ad8350 + enbl (5v) +v s (5v to 10v) c5 0.1f c4 0.001f c3 0.001f load z = 200 c2 0.001f source z = 200 c1 0.001f figure 2. basic connections for single-ended drive reactive matching in practical applications, the ad8350 will most likely be matched using reactive matching components as shown in figure 3. matching components can be calculated using a smith chart or by using a resonant approach to determine the matching network that results in a complex conjugate match. in either situation, the circuit can be analyzed as a single-ended equivalent circuit to ease calculations as shown in figure 4. v s 876 5 1234 ad8350 + enbl (5v) +v s (5v to 10v) 0.1f r load c ac c ac c p l s /2 l s /2 r s /2 r s /2 c ac c ac c p l s /2 l s /2 figure 3. reactively matching the input and output v s 876 5 1234 ad8350 + enbl (5v) +v s (5v to 10v) 0.1f r load c ac c p l s r s c ac c p l s c ac c ac figure 4. single-ended equivalent circuit when the source impedance is smaller than the load impedance, a step-up matching network is required. a typical step-up network is shown on the input of the ad8350 in figure 3. for purely resistive source and load impedances the reso nant approach may be used. the input and output impedance of the ad8350 can be modeled as a real 200 ? resistance for operating frequencies less than 100 mhz. for signal frequencies exceeding 100 mhz, classi- cal smith chart matching techniques should be invoked in order to deal with the complex impedance relationships. detailed s parameter data measured differentially in a 200 ? system can be found in tables ii and iii. for the input matching network the source resistance is less than the input resistance of the ad8350. the ad8350 has a nominal 200 ? input resistance from pins 1 to 8. the reactance of the ac-coupling capacitors, c ac , should be negligible if 100 nf capacitors are used and the lowest signal frequency is greater than 1 mhz. if the series reactance of the matching network inductor is defined to be x s = 2 f l s , and the shunt reactance of the matching capacitor to be x p = (2 f c p ) ? , then: x rr x xr r rr s s load p pload s load s = = where (1) for a 70 mhz application with a 50 ? source resistance, and assuming the input impedance is 200 ? , or r load = r in = 200 ? , then x p = 115.5 ? and x s = 86.6 ? , which results in the follow- ing component values: c p = (2 70 10 6 115.5) 1 = 19.7 pf and l s = 86.6 (2 70 10 6 ) 1 = 197 nh b
rev. ad8350 C9C for the output matching network, if the output source resis- tance of the ad8350 is greater than the terminating load resistance, a step-down network should be employed as shown on the output of figure 3. for a step-down matching network, the series and parallel reactances are calculated as: x rr x xr r rr s s load p ps load s load = = where (2) for a 10 mhz application with the 200 ? output source r esistance of the ad8350, r s = 200 ? , and a 50 ? load termination, r load = 50 ? , then x p = 115.5 ? and x s = 86.6 ? , which results in the following component values: c p = (2 10 10 6 115.5) 1 = 138 pf and l s = 86.6 (2 10 10 6 ) 1 = 1.38 h the same results can be obtained using the plots in figure 5 and figure 6. figure 5 shows the normalized shunt reactance versus the normalized source resistance for a ste p-up matching network, r s < r load . by inspection, the appropriate reactance can be found for a given value of r s /r load . the series reactance is then calculated using x s = r s r load /x p. the same technique can be used to design the step-down matching network using figure 6. 2 1.8 1.6 1.4 1.2 1 0.8 0.6 0.4 0.2 0 0.01 0.05 0.09 0.13 0.17 0.21 0.25 0.29 0.33 0.37 0.41 0.45 0.49 0.53 0.57 0.61 0.65 0.69 0.73 0.77 normalized reactance x p /r load normalized source resistance r source /r load r source x s r load x p figure 5. normalized step-up matching components normalized reactance x p /r load normalized source resistance r source /r load 3.2 3 2.8 2.6 2.4 2.2 2 2 2.4 2.8 3.2 3.6 4 4.4 4.8 5.2 5.6 6 6.4 6.8 7.2 7.6 8 8.4 8.8 r source x s r load x p figure 6. normalized step-down matching components the same results could be found using a smith chart as shown in figure 7. in this example, a shunt capacitor and a series inductor are used to match the 200 ? source to a 50 ? load. for a fre- quency of 10 mhz, the same capacitor and inductor values previously found using the resonant approach will transform the 200 ? source to match the 50 ? load. at frequencies exceeding 100 mhz, the s parameters from tables ii and iii should be used to account for the complex impedance relationships. source load shunt c series l figure 7. smith chart representation of step-down network after determining the matching network for the single-ended equivalent circuit, the matching elements need to be applied in a diff erential manner. the series reactance needs to be split such that the final network is balanced. in the previous examples, this simply translates to splitting the series ind uctor into two equal halves as shown in figure 3. gain adjustment the effective gain of the ad8350 can be reduced using a num- ber of techniques. obviously a matched attenuator network will reduce the effective gain, but this requires the addition of a separate component which can be prohibitive in size and cost. the attenuator will also increase the effective noise figure resu lting in an snr degradation. a simple voltage divider can be imple- mented using the combination of the driving impedance of the previous stage and a shunt resistor across the inputs of the ad8350 as shown in figure 8. this provides a compact solution but suffers from an increased noise spectral density at the input of the ad8350 due to the thermal noise contribution of the shunt resistor. the input impedance can be dynamically altered through the use of feedback resistors as shown in figure 9. this will result in a similar attenuation of the input signal by virtue of the voltage divider established from the driving source imped- ance and the reduced input impedance of the ad8350. yet this technique does not significantly degrade the snr with the unn ecessary increase in thermal noise that arises from a truly resistive attenuator network. b
rev. ad8350 C10C v s 876 5 1234 ad8350 + enbl (5v) +v s (5v to 10v) 0.1f c ac r s c ac c ac c ac r shunt r shunt r s r l r l figure 8. gain reduction using shunt resistor v s 876 5 1234 ad8350 + enbl (5v) +v s (5v to 10v) 0.1f r s c ac c ac r s r l r l c ac c ac r fext r fext figure 9. dynamic gain reduction figure 8 shows a typical implementation of the shunt divider concept. the reduced input impedance that results from the parallel combination of the shunt resistor and the input impedance of the ad8350 adds attenuation to the input signal effectively reducing the gain. for frequencies less than 100 mhz, the input impedance of the ad8350 can be modeled as a real 200 ? resis- tance (differential). assuming the frequency is low enough to ignore the shunt react ance of the input, and high enough such that the reactance of moderately sized ac-coupling capacitors can be considered negligible, the insertion loss, il, due to the shunt divider can be expressed as: il db log r rr rr rr r rr rr rr r gl nded in in s in shunt in shunt s in shunt in shunt in shunt in () () () = + + ? ? ? ? ? ? ? ? ? ? ? ? = + =? 20 100 10 where and ? sin e e (3) the insertion loss and the resultant power gain for multiple shunt resistor values is summarized in table i. the source resistance and input impedance need careful attention when using equation 1. the reactance of the input impedance of the ad8350 and the ac-coupling capacitors need to be considered before assuming they have negligible contribution. figure 10 shows the effective power gain for multiple values of r shunt for the ad8350-15 and ad8350-20. table i. gain adjustment using shunt resistor, r s = 100 and r in = 100 single-ended power gain?b r shunt il?b ad8350-15 ad8350-20 50 6.02 8.98 13.98 100 3.52 11.48 16.48 200 1.94 13.06 18.06 300 1.34 13.66 18.66 400 1.02 13.98 18.98 r shunt 20 0 gain db 18 16 14 12 10 8 6 4 2 0 100 200 300 400 500 600 700 800 ad8350-20 ad8350-15 figure 10. gain for multiple values of shunt resistance for circuit in figure 8 the gain can be adjusted dynamically by employing external feedback resistors as shown in figure 9. the effective attenua- tion is a result of the lowered input impedance as with the shunt resistor method, yet there is no additional noise contribution at the input of the device. it is necessary to use well-matched resistors to minimize common-mode offset errors. quality 1% tolerance resistors should be used along with a symmetric board layout to help guarantee balanced performance. the effective gain for mul- tiple values of external feedback resistors is shown in figure 11. b
rev. ad8350 C11C r fext 20 0 gain db 18 16 14 12 10 8 6 4 2 0 500 1000 1500 2000 ad8350-20 ad8350-15 figure 11. p ower gain vs. external feedback resistors for the ad8350-15 and ad8350-20 with r s = 100 ? and r l = 100 ? the power gain of any two-port network is dependent on the source and load impedance. the effective gain will change if the differential source and load impedance is not 200 ? . the single- ended input and output resistance of the ad8350 can be modeled using the following equations: r rr rr r gr in fl fl int ml = + + ? ? ? ? ? ? ++ 1 (4) and r r rr g rr rr gr for r k out f s int m s int fs ms s = + + + + ? ? ? ? ? ? ? ? ? ? + + 1 11 1 1 11 1 1 ? (5) where r f =r fext //r fint r fext = r feedback external r fint = 662 ? for the ad8350-15 = 1100 ? for the ad8350-20 r int = 25000 ? g m = 0.066 mhos for the ad8350-15 = 0.110 mhos for the ad8350-20 r s = r source (single-ended) r l = r load (single-ended) r in = r input (single-ended) r out = r output (single-ended) the resultant single-ended gain can be calculated using the following equation: g rgr rrrrrg v lmf lsf lsm = ? () ++ + 1 (6) driving lighter loads it is not necessary to load the output of the ad8350 with a 200 ? differential load. often it is desirable to try to achieve a complex conjugate match between the source and load in order to minimize reflections and conserve power. but if the ad8350 is driving a voltage responding device, such as an adc, it is no longer necessary to maximize power transfer. the harmonic disto rtion performance will actually improve when driving loads greater than 200 ? . the lighter load requires less cur- rent driving capability on the output stages of the ad8350 resulting in im proved linearity. figure 12 shows the improve- ment in second and third harmonic distortion for increasing differential load resistance. r load 66 200 distortion dbc 68 70 72 74 76 78 80 82 300 400 500 600 700 800 900 1000 hd3 hd2 figure 12. second and third harmonic distortion vs. differential load resistance for the ad8350-15 with v s = 5 v, f = 70 mhz, and v out = 1 v p-p b
rev. ad8350 C C table ii. typical scattering parameters for the ad8350-15: v cc = 5 v, differential input and output, z source (diff) = 200 , z load (diff) = 200 frequency ?mhz s11 s12 s21 s22 25 0.015 48.8 0.119 176.3 5.60 4.3 0.034 4.8 50 0.028 65.7 0.119 171.1 5.61 8.9 0.032 14.3 75 0.043 75.3 0.119 166.9 5.61 13.5 0.036 30.2 100 0.057 87.5 0.120 163.5 5.61 17.9 0.043 39.6 125 0.073 91.8 0.119 159.8 5.65 22.6 0.053 40.6 150 0.080 95.6 0.120 154.8 5.68 27.0 0.058 37 175 0.100 97.4 0.117 151.2 5.73 31.8 0.072 45.1 200 0.111 99.1 0.121 147.3 5.78 36.3 0.077 47.7 225 0.128 103.2 0.120 143.7 5.83 41.0 0.091 52.5 250 0.141 106.7 0.120 140.3 5.90 45.6 0.104 55.1 275 0.151 109.7 0.120 136.6 6.02 50.2 0.108 54.2 300 0.161 111.9 0.123 132.9 6.14 55.1 0.122 51.5 325 0.179 114.7 0.121 130.7 6.19 60.2 0.135 55.6 350 0.187 117.4 0.122 126.6 6.27 65.0 0.150 56.9 375 0.194 121 0.123 123.6 6.43 70.1 0.162 60.9 400 0.199 121.2 0.124 120.1 6.61 75.8 0.187 60.3 425 0.215 122.6 0.126 117.2 6.77 81.7 0.215 63.3 450 0.225 127.0 0.126 113.9 6.91 87.6 0.242 63.9 475 0.225 127.7 0.126 112 7.06 93.8 0.268 65.2 500 0.244 129.9 0.128 108.1 7.27 99.8 0.304 68.2 table iii. typical scattering parameters for the ad8350-20: v cc = 5 v, differential input and output, z source (diff) = 200 , z load (diff) = 200 frequency ?mhz s11 s12 s21 s22 25 0.017 142.9 0.074 174.9 9.96 4.27 0.023 16.6 50 0.033 114.9 0.074 171.0 9.98 8.9 0.022 2.7 75 0.055 110.6 0.075 167.0 9.98 13.3 0.023 23.5 100 0.073 109.4 0.075 163.1 10.00 17.7 0.029 22.7 125 0.089 112.1 0.075 159.2 10.12 22.1 0.037 18.0 150 0.098 116.5 0.076 153.8 10.20 26.4 0.045 3.2 175 0.124 118.1 0.075 150.2 10.34 30.9 0.055 15.7 200 0.141 119.4 0.076 147.2 10.50 35.6 0.065 15.6 225 0.159 122.6 0.077 142.2 10.65 40.1 0.080 17.7 250 0.170 128.5 0.078 139.5 10.80 44.7 0.085 22.4 275 0.186 131.6 0.078 135.8 11.14 49.3 0.096 23.5 300 0.203 132.9 0.080 132.5 11.45 54.7 0.116 25.9 325 0.215 135.0 0.080 129.3 11.70 60.3 0.139 29.6 350 0.222 136.9 0.082 125.9 11.93 65.0 0.161 32.2 375 0.242 142.4 0.082 123.6 12.39 70.3 0.173 38.6 400 0.240 145.2 0.084 120.3 12.99 76.8 0.207 37.6 425 0.267 146.7 0.084 117.3 13.34 84.0 0.241 48.1 450 0.266 150.7 0.086 115.1 13.76 90.1 0.265 49.7 475 0.267 153.7 0.087 112.8 14.34 97.5 0.317 53.5 500 0.285 161.1 0.088 110.9 14.89 105.0 0.359 59.2 b 12
ad8350 rev. b | page 13 outline dimensions figure 14. 8-lead standard small outline package [soic_n] narrow body (r-8) dimensions shown in millimeters and (inches) figure 15. 8-lead mini small outline package [msop] (rm-8) dimensions shown in millimeters controlling dimensions are in millimeters; inch dimensions (in parentheses) are rounded-off millimeter equivalents for reference only and are not appropriate for use in design. compliant to jedec standards ms-012-aa 012407-a 0.25 (0.0098) 0.17 (0.0067) 1.27 (0.0500) 0.40 (0.0157) 0.50 (0.0196) 0.25 (0.0099) 45 8 0 1.75 (0.0688) 1.35 (0.0532) seating plane 0.25 (0.0098) 0.10 (0.0040) 4 1 85 5.00 (0.1968) 4.80 (0.1890) 4.00 (0.1574) 3.80 (0.1497) 1.27 (0.0500) bsc 6.20 (0.2441) 5.80 (0.2284) 0.51 (0.0201) 0.31 (0.0122) coplanarity 0.10 compliant to jedec standards mo-187-aa 6 0 0.80 0.55 0.40 4 8 1 5 0.65 bsc 0.40 0.25 1.10 max 3.20 3.00 2.80 coplanarity 0.10 0.23 0.09 3.20 3.00 2.80 5.15 4.90 4.65 pin 1 identifier 15 max 0.95 0.85 0.75 0.15 0.05 10-07-2009-b
ad8350 rev. b | page 14 ordering guide model 1 temperature range package description package option branding ad8350arz15-reel7 ?40c to +85c 8-lead soic_n r-8 ad8350armz15 ?40c to +85c 8-lead msop rm-8 q0t AD8350ARMZ15-REEL7 ?40c to +85c 8-lead msop rm-8 q0t ad8350armz20 ?40c to +85c 8-lead msop rm-8 q0u ad8350armz20-reel7 ?40c to +85c 8-lead msop rm-8 q0u ad8350arm20-reel7 ?40c to +85c 8-lead msop rm-8 j2p ad8350arz20-reel7 ?40c to +85c 8-lead soic_n r-8 1 z = rohs compliant part. revision history 5/13rev. a to rev. b deleted evaluation board section ................................................ 12 updated outline dimensions ....................................................... 13 changes to ordering guide .......................................................... 14 6/01rev. 0 to rev. a ?2013 analog devices, inc. all rights reserved. trademarks and registered trademarks are the prop erty of their respective owners. d01014-0-5/13(b)

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